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532 Measurements and adjustment techniques RF signal is both unmodulated and sinusoidal Otherwise, the readings are meaningless unless calibrated against some other source It is also possible to use various bridge methods for measurement of RF power Figure 27-13 shows a bridge set up to measure both forward and reverse power This circuit was once popular for VSWR meters There are four elements in this quasiWheatstone bridge circuit: R1, R2 , R3, and the antenna impedance (connected to the bridge at J2) If Rant is the antenna resistance, then we know that the bridge is in balance (ie, the null condition) when the ratios R1/R2 and R3/Rant are equal In an ideal situation, resistor R3 will have a resistance equal to Rant , but that might overly limit the usefulness of the bridge In some cases, therefore, the bridge will use a compromise value such as 67 for R3 Such a resistor will be usable on both 50- and 75- antenna systems with only small errors Typically, these meters are designed to read relative power level, rather than the actual power An advantage of this type of meter is that we can get an accurate measurement of VSWR by proper calibration With the switch in the forward position, and RF power applied to J1 (XMTR), potentiometer R6 is adjusted to produce a full-scale deflection on meter M1 When the switch is then set to the reverse position, the meter will read reverse power relative to the VSWR An appropriate VSWR scale is provided
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R1 47 k C2 001 F
D1 IN60 or IN34
RANT
R2 47 k R7 47 k FWD REV S1 M1 0-100 A R6 50 k C1 001 F
R4 47 k R5 1k
27-13 A bridge arrangement to measure both forward and reverse power
Selecting and using RF wattmeters and antenna VSWR meters 533 A significant problem with the bridge of Fig 27-13 is that it cannot be left in the circuit while transmitting because it dissipates a considerable amount of RF power in the internal resistances These meters, during the time when they were popular, were provided with switches that bypassed the bridge when transmitting The bridge was only in the circuit when making a measurement An improved bridge circuit is the capacitor/resistor bridge in Fig 27-14; this circuit is called the micromatch bridge Immediately, we see that the micromatch is improved over the conventional bridge because it uses only 1 in series with the line (Ri) This resistor dissipates considerably less power than the resistance used in the previous example Because of this low-value resistance, we can leave the micromatch in the line while transmitting Recall that the ratios of the bridge arms must be equal for the null condition to occur In this case, the capacitive reactance ratio of C1/C2 must match the resistance ratio R1/Rant For a 50- antenna, the ratio is 1 50, and for 75- antennas it is 1 75 (or, for the compromise situation, 1 68) The small-value trimmer capacitor (C2) must be adjusted for a reactance ratio with C1 of 1 50, 1 75, or 1 68, depending upon how the bridge is set up The sensitivity control can be used to calibrate the meter In one version of the micromatch, there are three power ranges (10, 100, and 1000 W) Each range has its own sensitivity control, and these are switched in and out of the circuit as needed The monomatch bridge circuit in Fig 27-15 is the instrument of choice for HF and low-VHF applications In the monomatch design, the transmission line is segment
J1 XMTR
R1 1
J2 ant
C1 820 pF SM
D1 IN60
C2 30 pF RFC2 1 mH R1 10 k sensitivity RFC1 1 mH M1 0 500 A
27-14 Micromatch wattmeter
534 Measurements and adjustment techniques
R1 100 k
CR2 IN60 C2 001 F R4 15 k
C J1 XMTR B A CR1 IN60 R3 15 k S1 FWD REV R2 100 J2 ant
C1 001 F
R5 10 k
M1 0-500 A C3 005 F
27-15 Monomatch wattmeter
B, while RF sampling elements are formed by segments A and C Although the original designs were based on a coaxial-cable sensor, later versions used either printed circuit foil transmission line segments or parallel brass rods for A, B, and C The sensor unit is basically a directional coupler with a detector element for both forward and reverse directions For best accuracy, diodes CR1 and CR2 should be matched, as should R1 and R2 The resistance of R1 and R2 should match the transmission line surge impedance, although in many instruments a 68- compromise resistance is used The particular circuit shown in Fig 27-15 uses a single dc meter movement to monitor the output power Many modern designs use two meters (one each for forward and reverse power) One of the latest designs in VSWR meter sensors is the current transformer assembly shown in Fig 27-16 In this instrument, a single-turn ferrite toroid transformer is used as the directional sensor The transmission line passing through the hole in the toroid doughnut forms the primary winding of a broadband RF transformer The secondary, which consists of 10 to 40 turns of small enamel wire, is connected to a measurement bridge circuit (C1 + C2 + load) with a rectified dc output Figures 27-17 and 27-18 show instruments based on the current transformer technique Shown in Fig 27-17 is the Heath model HM-102 high-frequency VSWR/power meter The sensor is a variant on the current transformer method This
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