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Pin Lm I min
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Converter input power Power transformer magnetizing Minimum primary current
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Vout Subcircuit output voltage
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1:NP V(15) VIN V(6) D
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LP F
V(3) VC
3 VEE 9 VCC 14
DELAY TS
CLK Q D R Q S
1:NC
1 2 5
V(45) VOUT
V(9) D
R1 RB
Figure 5.1 Flyback subcircuit schematic that can be used in both voltage and current modes with discontinuous and continuous inductor currents.
I max Fsw Ts Ton Vin
Peak primary current Switching frequency Ef ciency factor Propagation delay MOSFET on-time Converter input voltage
I out Rb NC D Pout
Average output current Current transformer burden Current transformer ratio Converter duty cycle Converter output power
Governing equations
Pout = Pin Pin = 1 2 2 L m Imax Imin Fsw 2
Imax is de ned by the control Voltage Vc as Imax = VC NC Vin Ts + Rb Lm
The MOSFET on-time is calculated as Ton = Since Ton = D/Fsw , D= Lm Fsw ( Imax Imin ) Vin NP Vout Lm ( Imax Imin ) Vin
Flyback Converters
During the MOSFET off-time, the primary current falls as Imax Imin = Substituting equations, Imin = Imax Vout NP 1 L m Fsw Vin ( Imax Imin ) Vout 1 D NP Lm Fsw while Imax Imin 0
which can be further simpli ed as Imin = Imax NP L m Fsw Substituting equations, Iout =
2 2 L m Fsw Imax Imin 2
Vout Vout 1+ NP Vin
while
Imin 0
1 1 + Vout Vin NP Vout
and the duty cycle can be calculated as D= L m Fsw ( Imax Imin ) Vin NP Vout
The circuit shown in Fig. 5.2 is a simple representation, using the new subcircuit, of a dual-output yback converter with a separate transformer winding for voltage regulation. The yback subcircuit essentially replaces the PWM switch model discussed in Chap. 4. The results of the gain-phase measurement of the yback converter are shown in Figs. 5.3 and 5.4 for a 30-mA load and a 1-A load on each output, respectively. The circuit has a bandwidth of 7 kHz with a phase margin of 75 and a 1-A load. At a 30-mA load, the performance is quite different because of the discontinuous operation. The 34 kHz would likely be a problem for most applications. Either the converter would require a preload or the 1-A load bandwidth would have to be reduced. This would sacri ce performance. Note that L1 and C4 are used to break the loop for the open-loop measurement. Voltage source V4 represents the injection signal. This method allows the DC path to be closed via L1, while the AC information is removed (essentially) by the very low frequency lter created by L1 and C4. Audio Susceptibility The same SPICE model can be used to evaluate closed-loop performance parameters, such as audio susceptibility. To use the model for these
Five
X1 FLYBACK FLYBACK
V(11) +15 X3 TURNS VOUT
2 13
X4 TURNS
D1 DN5806
V1 28 VC
15 17
C1 100U RTN DUTY
R1 450
+C4 10
V4 AC L1 10
V(5) D
V(6) FDBCK X7 UC1843AS
14 16 VC 6 OUT GND REF COMP FDBK 8 21
C2 100U R6 47K R4 8K
R2 450
C3 1N
V(3) SENSE
X5 TURNS
D2 DN5806 V(18) -15
V3 15
R5 2.5K R3 1MEG
X6 TURNS
FLY1: DUAL OUTPUT FLYBACK CONVERTER .TRAN 10U 2M .AC DEC 25 100 1MEG .DC V1 18 38 .1 .OPTIONS RELTOL=.01 ITL1=500 ITL2=500 ITL4=500 GMIN=1n .NODESET V(2)=15.7 .PROBE V(11)=+15 V(3)=SENSE V(6)=FDBCK V(18)=-15 V(5)=D .PRINT AC V(11) VP(11) V(3) VP(3) .PRINT AC V(6) VP(6) .PRINT TRAN V(3) V(18) .PRINT DC V(17) V1 1 0 28 ; add AC 1 for Audio Susceptibility Test X3 2 0 13 4 TURNS Params: NUM=18 X4 9 0 13 4 TURNS Params: NUM=18 X5 0 7 13 4 TURNS Params: NUM=18 X6 3 0 13 4 TURNS Params: NUM=12 D1 9 11 DN5806 D2 18 7 DN5806 C1 11 0 100U C2 0 18 100U R1 11 0 15 ; 15 ohms for 1A, 450 for 30ma R2 0 18 15 ; 15 ohms for 1A, 450 for 30ma R3 4 0 1MEG X7 8 21 0 6 16 14 UC1843AS VEA 6 60 10m ; Added for convergence at low currents
Schematic design and netlist for a dual-output yback converter.
Flyback Converters
R4 3 21 8K R5 21 0 2.5K C3 8 12 1N R6 12 21 47K V3 16 0 15 L1 17 60 10 ; 10 for open loop Gain/Phase analysis, 1p for Closed loop analysis (Transient or Audio Susceptibility) C4 15 17 10 ; 10 for open loop Gain/Phase analysis, 1p for Closed loop analysis (Transient or Audio Susceptibility) V4 15 0 AC 1 X1 1 0 17 2 5 FLYBACK Params: L=20U NC=100 NP=1 F=250K EFF=1 RB=10 + TS=.25U .END
(Continued).
evaluations, the inductor, capacitor, and AC voltage source can be left in the circuit. This is accomplished by changing the value of L1 to 1 pH, and C4 to 1 pF. To simulate the audio susceptibility performance, an AC source statement must also be added to the input voltage source, V1. The results of the audio susceptibility simulation are shown in the graph of Fig. 5.5.
Wfm1: Gain in dB (Volts)
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