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B3 V=V(14)> 10 : 0
L1 10M
17 16
V(16) X6 KBPC806
24 3 2
C3 1U
C4 220P
R8 V=V(14)
C5 1M
R10 150
R9 1.5K B4 V=V(15)> 0 10 : 0
UPS4: TO POWER A NON-LINEAR LOAD .TRAN 9.766U 10M UIC .FOUR 400HZ V(13) .PROBE V(1)=OUT V(15)=Q V(7)=FLTR1 .PRINT TRAN V(1) V(15) V(7) V(3) R1 15 7 4.7K C1 7 0 47N IC=0 V1 4 0 PULSE -2.5 2.5 10N 10N 10N 5U 9.766U V2 5 0 SIN 0 1.5 400 R4 5 0 1MEG R5 7 1 47K C2 1 0 8.2N IC=0 EB1 6 0 Value={ IF ( (V(5)-V(19)) > 0 , 2.5 , -2.5 ) } X2 18 0 8 11 10 XFMR-TAP Params: RATIO=.1 X4 10 0 2 SWITCH V3 11 0 24 L1 18 3 10M C3 3 0 1U X3 8 0 12 SWITCH EB3 12 0 Value={ IF ( V(14) > 0 , 10 , 0 ) } EB4 2 0 Value={ IF ( V(15) > 0 , 10 , 0 ) } R8 3 19 161K R9 19 0 1.5K C4 3 19 220P X6 3 0 9 13 KBPC806 C5 9 13 1M IC=140 R10 9 13 150 X1 4 6 0 0 14 15 FFLOPZero .END
Figure 7.12b Schematic and netlist of the push-pull converter driving a nonlinear load. Improved con guration similar to Fig. 7.10.
DC-to-AC Conversions
Improved V(3) in Volts
Original V(3) in Volts
Wfm1:
Wfm2:
1.00M
3.00M
5.00M
7.00M
9.00M
Time in Secs
Simulation results of the circuits in Figs. 7.12b (waveform 1) and 7.12a (wave-
form 2).
demonstrate the behavior of both the original circuit (Fig. 7.7) and the improved circuit (Fig. 7.10) when they are used to power a nonlinear load. The upper trace shows the result of our improved circuit, while the lower trace shows the results of the original circuit. Both of the simulations resulted in the same peak output amplitude, which has been reduced to 142 V as a result of the high current demand by the nonlinear load. The major difference between the two circuits is the output wave shape. The improved circuit maintains the sinusoidal wave shape throughout the waveform, with the exception of the attened peaks. The original circuit produces a square wave as a result of the unloaded condition that occurs throughout the waveform except at the peaks. The end result is a major difference in the RMS amplitude (108 and 127 V, respectively). The increased RMS voltage of the original circuit can easily cause the saturation of transformers within the load. The increased RMS voltage may also stress other components which are sensitive to the RMS content of the load. Three-Phase Sine Reference The circuit example in Fig. 7.14 demonstrates a three-phase sine-wave reference using the mixed-mode simulation techniques. A six-stage shift register is used to generate three quasi-square waves that are exactly
Seven
V(2) CLK X1 FFLOP
X2 FFLOP
X3 FFLOP
X4 FFLOP
X5 FFLOP
X6 FFLOP
CLK Q D R Q S
CLK Q D R Q S
CLK Q D R Q S
CLK Q D R Q S
CLK Q D R Q S
CLK Q D R Q S
V2 PULSE
R1 380K
R4 190K
V4 -15 C3 1200P
22 16 VEE
C4 2200P R2 380K
X7 UA741
R5 190K
3.92 V(32) A C5 1500P Tran 0 836M 2.00M time 7.00M
VCC 15
V3 15
R6 380K
R8 190K
V6 -15 C6 1200P X8 UA741
23 20 VEE
R9 190K
3.97 V(24) B C8 1500P Tran 0 833M 2.00M time 7.00M
R7 380K
VCC 21
V5 15
R10 380K
R12 190K
V8 -15 C9 1200P
29 27 VEE
X9 UA741
R11 380K
R13 190K
3.97 V(34) C C11 1500P Tran 0 833M 2.00M time 7.00M
VCC 28
V7 15
Schematic and netlist for a three-phase sine-wave reference.
DC-to-AC Conversions
3PHASE: A THREE PHASE SINE WAVE .PROBE .TRAN 1U 7M ; UIC .FOUR 500HZ V(32) V(3)=Q1 V(1)=Q2 V(2)=CLK V(32)=A V(24)=B V(30)=C .PRINT TRAN V(3) V(1) V(2) V(32) .PRINT TRAN V(24) V(30) V(33) V4 22 0 DC=-15 X6 2 9 0 0 12 13 FFLOPFive V5 21 0 DC=15 C3 16 0 1200P X7 18 16 18 15 22 UA741 R1 3 14 380K V6 23 0 DC=-15 X8 19 20 19 21 23 UA741 C4 14 18 2200P R2 1 14 380K V7 28 0 DC=15 X9 26 27 26 28 29 UA741 C5 32 0 1500P V8 29 0 DC=-15 C6 20 0 1200P R4 14 16 190K C7 25 19 2200P R5 18 32 190K C8 24 0 1500P R6 33 25 380K C9 27 0 1200P R7 7 25 380K R8 25 20 190K R9 19 24 190K X1 2 8 0 0 5 3 FFLOPFive R10 9 31 380K X2 2 3 0 0 6 1 FFLOPFive R11 13 31 380K X3 2 1 0 0 8 33 FFLOPFive C10 31 26 2200P R12 31 27 190K X4 2 33 0 0 10 7 FFLOPFive V2 2 0 PULSE 0 5 100N 10N 10N 100U 333.33U C11 30 0 1500P R13 26 30 190K V3 15 0 DC=15 X5 2 7 0 0 11 9 FFLOPFive .END
(Continued )
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