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V1 19 Tran Generators = SIN
V4 IFET
D2 40EPS08
S Clk Q
X2 FFLOP
4 12
R10 4.7
R4 20m X3 IXFH32N50
I(V2) < 50m 5: 0
B2 Voltage
B1 Voltage V(4) > 2.5 15 : 0
B3 Voltage I(V2) > V(3)/26 5: 0
Critical PFC.cir .TRAN 1U 3.75m 1.25m .01u UIC .PROBE .FOUR 400 I(V1) R2 vout 0 225 V2 2 9 R3 3 2 1m L1B 1 9 100u V4 1 10 EB3 16 0 Value={ IF(I(V2) > V(3)/26 , 5 , 0) } D2 1 11 40EPS08 V1 7 19 DC=163 SIN 0 163 400 C2 vout 13 1000u IC=250 R1 2 0 10k V3 11 vout R4 13 0 20m X3 10 6 0 IXFH32N50 X4 8 19 3 0 KBPC808 EB1 5 0 Value={ IF(V(4) > 2.5 , 15 , 0) } EB2 14 0 Value={ IF (I(V2) < 50m , 5 , 0) } RT14 14 0 1G X2 0 0 16 14 12 4 FFLOP C7 8 19 1u L3 7 8 100u R10 5 6 4.7 .END
Critical conduction boost power factor corrector and netlist.
Eight
1 v(10)
id(d2)
i(v4)
Mosfet Drain Voltage
30.0 240
20.0 Plot1 id(d2), i(v4) in amperes
40.0 1 v(10) in volts
Diode Current Mosfet Current
3.216m
3.218m
3.220m Time in Secs
3.222m
3.224m
Critical conduction boost waveforms.
i(v1)
product
difference
1.60k
80. 0
Input Voltage
1.20k
Input Current
difference in volts i(v1) in amperes Plot1 product in watts
Input Power
-10. 0
1.50m
2.00m
2.50m Time in Secs
3.00m
3.50m
Critical conduction boost input current.
Power Factor Correction
IV2 L3 250u
V2 C7 1u Inp
X4 KBPC808
C9 .01u
Vrect RAC 680k IAC
C8 3u V1 Tran Generators = SIN
Rff1 910k
R4 170k
vref
R10 10 Inm
C4 .15u
R8 100k VRMS C1 1u Rff2 18k
C2 62p CAO
Isense R7 3.01K pklmt CAO
X5 UC3854B
G ND PKLIM CA OUT ISENS MO UT DUTY VCC CT SS RSET VSENSE ENA VREF
duty
VMOUT out R6 vsense R24 1meg 180k
MOUT IAC
vsense
R19 8.2k R11 1.5k R12 6.2k pklmt
VAOut
RMO 3.01K VRMS
IAC VA OUT VRMS
vref
C10 .1u V13 Vrect
gnd X3 IDiode HFA25TB60
out vout R25 300
R23 .1 gnd duty
X2 PWMBST
C6 470u
Transient (steady state) simulation of a boost power factor corrector circuit using a state space model of UC3854. FOURIER COMPONENTS OF TRANSIENT RESPONSE I(V1) DC COMPONENT = 9.193709E-06 HARMONIC FREQUENCY FOURIER NORMALIZED PHASE NORMALIZED NO (HZ) COMPONENT COMPONENT (DEG) PHASE(DEG) 1 4.000E+02 3.421E+00 1.000E+00 6.626E+00 0.000E+00 2 8.000E+02 1.849E-04 5.405E-05 1.742E+02 1.609E+02 3 1.200E+03 3.140E-02 9.178E-03 1.769E+02 1.570E+02 4 1.600E+03 2.670E-04 7.804E-05 -9.829E+01 -1.248E+02 5 2.000E+03 4.432E-03 1.296E-03 -1.743E+02 -2.075E+02 6 2.400E+03 6.726E-05 1.966E-05 6.698E+01 2.722E+01 7 2.800E+03 4.988E-03 1.458E-03 1.774E+02 1.310E+02 8 3.200E+03 9.157E-05 2.677E-05 -1.508E+02 -2.038E+02 9 3.600E+03 3.411E-03 9.971E-04 1.764E+02 1.168E+02 TOTAL HARMONIC DISTORTION = 9.436542E-01 PERCENT
Eight
UC3854 State Space PFC.cir .TRAN 1u 250m 230m 10u UIC .PROBE .FOUR 60 I(V2) V1 1 Inm DC=90 SIN 0 150 60 0 0 0 X4 Inp Inm Vrect gnd KBPC808 C7 3 Inm 1u L3 1 3 250u C8 3 4 3u R10 4 Inm 10 Rff1 Vrect 17 910k Rff2 VRMS 0 18k RAC Vrect IAC 680k R4 IAC vref 170k R6 out vsense 1meg R11 0 pklmt 1.5k X3 13 out HFA25TB60 V2 3 Inp C1 VRMS 0 1u IC=1 X5 0 pklmt CAO Isense MOUT IAC VAOut VRMS vref vsense duty + UC3854Bs R24 vsense VAOut 180k RMO MOUT gnd 3.01K C10 vsense VAOut .1u IC=0 C2 CAO Isense 62p IC=0 R7 0 Isense 3.01K R8 17 VRMS 100k C4 17 0 .15u IC=7 R12 pklmt vref 6.2k R19 vsense 0 8.2k C9 Vrect 0 .01u R23 0 gnd .1 X2 Vrect 0 43 0 duty PWMBST C6 out 0 470u IC=375 R25 out 0 300 V13 43 13 .END FOURIER COMPONENTS OF TRANSIENT RESPONSE I(V2) DC COMPONENT = 1.039190E-04 HARMONIC FREQUENCY FOURIER NORMALIZED PHASE NORMALIZED NO (HZ) COMPONENT COMPONENT (DEG) PHASE (DEG) 1 6.000E+01 6.002E+00 1.000E+00 -1.343E-01 0.000E+00 2 1.200E+02 2.381E-04 3.967E-05 -5.550E+01 -5.523E+01 3 1.800E+02 1.400E-01 2.332E-02 -1.757E+02 -1.753E+02 4 2.400E+02 1.094E-04 1.822E-05 -7.497E+01 -7.443E+01 5 3.000E+02 3.560E-02 5.930E-03 -1.776E+02 -1.770E+02 6 3.600E+02 8.766E-05 1.460E-05 -8.850E+01 -8.770E+01 7 4.200E+02 2.760E-02 4.599E-03 -1.772E+02 -1.762E+02 8 4.800E+02 7.394E-05 1.232E-05 -1.015E+02 -1.004E+02 9 5.400E+02 2.400E-02 3.998E-03 -1.775E+02 -1.762E+02
TOTAL HARMONIC DISTORTION = 2.482531E+00 PERCENT Boost power factor corrector results.
Power Factor Correction
i(l3)
product
difference
4.00k
3.00k
Input Current 4.403 Arms
Input Voltage = 106 Vrms
difference in volts
product in watts
Plot1 i(l3) in amperes
3rd Harmonic Distortion
-320 1
2.00k
Input Power 466.6 Watts
-9.00 1.00k -520
232m
236m
240m Time in Secs
244m
248m
(Continued )
Critical Conduction Power Factor Corrector One of the major limitations of the boost converter is the output recti er diode. The diode must have a high enough voltage rating to support the output voltage and is abruptly switched with the output current owing through it. This leads to a very high loss in both the recti er and the MOSFET switch. Technology is continuously working to improve these high-voltage diodes; however, there is another option that is becoming more widespread. This is the critical conduction boost PFC. The critical conduction boost converter operates at the boundary of continuous and discontinuous operation. This is achieved by the use of a zero-crossing detector, which determines the point at which the inductor current has reduced to near zero. At this point the MOSFET can be turned on without a recovery effect in the output recti er, signi cantly reducing the losses in both the MOSFET and the diode. Critical conduction PFC controllers are now available from several manufacturers. Two of the most popular are the MC33262 from ON Semiconductor and the TDA4863 from In neon. A simpli ed SPICE model of a critical conduction mode boost PFC is shown in Fig. 8.10. In this simulation the latch is set when the current in the inductor falls to 50 mA. The latch is reset when the inductor current reaches a
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