barcode fonts for ssrs The Miller capacitance CM is the input shunt capacitance suggested by (8.46): CM 1 KF 2 in Software

Creator Code 39 in Software The Miller capacitance CM is the input shunt capacitance suggested by (8.46): CM 1 KF 2

The Miller capacitance CM is the input shunt capacitance suggested by (8.46): CM 1 KF 2
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since comparison of Figs. 8-9(a) and 8-12(a) shows that C forms a feedback path analogous to YF . (b) The output shunt capacitance, as suggested by (8.48), must also be determined. Since hre 0 underlies the hybrid- model, the reverse voltage-gain ratio KR 0, hence: Yo Y2 1 KR YF % Y2 YF Y2 sC 3
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Comparison of Fig. 8-9(a) with Fig. 8-12(b) and the use of (1) to (3) lead to the equivalent circuit of Fig. 8-25. Let Ceq CM C 1 gm RC C C Then, by voltage division, Vb 0 e and by Ohm s law, VL RC kRL g V 0 s RC kRL C 1 m b e 5 r = sr Ceq 1 r = r r V  x V rx r = sr Ceq 1 s s rx kr Ceq 1 s 4
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Substitution of (4) into (5) and rearrangement yield the desired voltage-gain ratio: Av s VL gm RC kRL r = rx r s RC kRL C 1 s rx kr Ceq 1 Vs
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FREQUENCY EFFECTS IN AMPLIFIERS
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_ _ (1 + gm RC)Cm
gm Lb e
+ LL _
Fig. 8-25
(a) Apply the results of Section 8.6 to the small-signal equivalent circuit of Fig. 8-11 to determine the Miller admittance. (b) Utilizing the Miller admittance, draw the high-frequency small-signal equivalent circuit and determine the voltage-gain ratio.
(a) With load resistor RL and feedback capacitor Cgd removed from the circuit of Fig. 8-11, the forward gain KF follows from an application of Ohm s law: KF VL gm rds kRD s rds kRD Cds 1 Vgs  gm rds kRD s Cgd s rds kRD Cds 1 1
The Miller admittance suggested by (8.46) is  YM 1 KF YF 1 2
In the frequency range of interest and for typical values of rds ; RD ; and Cds , generally js rds kRD Cds j ( 1; thus, the Miller admittance can be synthesized as a capacitor with value CM YM 1 gm rds kRD Cgd s 3 Hence, the 4
(b) Since there is no feedback of output voltage to the input network of Fig. 8-11, KR 0. output admittance, as suggested by (8.48), is simply 1 KR YF YF sCgd
The equivalent circuit of Fig. 8-11 can be converted to the form of Fig. 8-12(b), as displayed in Fig. 8-26. By Ohm s law, VL gm Vgs s Cds Cgd gds GD GL 5
Since Vgs Vi , the required voltage-gain ratio follows as Av s VL gm Vi s Cds Cgd gds GD GL (See Problem 8.25.) 6
As long as the source resistance is negligible, Av is independent of CM .
RG _
gm Lgs
+ LL _
Fig. 8-26
CHAP. 8]
FREQUENCY EFFECTS IN AMPLIFIERS
The high-frequency equivalent circuit for the CS JFET ampli er of Fig. 4-5 is given by Fig. 8-11. Let RG 1 M; RL RD 2 k; rds 50 k; gm 0:016 S; Cgs 3 pF; Cds 1 pF; and Cgd 2:7 pF. By SPICE methods, determine the voltage gain for a 50 MHz impressed signal.
The netlist code below describes the circuit:
Prb8_20.CIR vi 1 0 AC 0.25V RG 1 0 1Megohm Cgs 1 0 3pF Cgd 1 2 2.7pF Ggm 2 0 (1,0) 0.016 rds 2 0 50kohm Cds 2 0 1pF RD 2 0 2kohm RL 2 0 2kohm .AC DEC 100 1MegHz 100MegHz .PROBE .END
Execute hPrb8_20.CIRi and use the Probe feature of PSpice to give Fig. 8-27. From the marked points, it is seen that the voltage gain at 50 MHz is Av 10:36 128:28
Fig. 8-27
For the CG JFET ampli er of Fig. 4-28, let VDD 15 V, R1 R2 10 k, RD 500 , RS 2 k, and CC1 CC2 15 F. Add a load resistor RL 15 k. The JFET is modeled by the parameters of Problem 4.4. Use SPICE methods to implement a wide frequency range study to determine low- and high-frequency cuto points for this ampli er.
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